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CS51033 Fast P-Ch FET Buck Controller
The CS51033 is a switching controller for use in DC-DC converters. It can be used in the buck topology with a minimum number of external components. The CS51033 consists of a 1.0 A power driver for controlling the gate of a discrete P-Channel transistor, fixed frequency oscillator, short circuit protection timer, programmable Soft-Start, precision reference, fast output voltage monitoring comparator, and output stage driver logic with latch. The high frequency oscillator allows the use of small inductors and output capacitors, minimizing PC board area and systems cost. The programmable Soft-Start reduces current surges at start up. The short circuit protection timer significantly reduces the P-Ch FET duty cycle to approximately 1/30 of its normal cycle during short circuit conditions.
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SOIC-8 D SUFFIX CASE 751
* * * * * * * *
1.0 A Totem Pole Output Driver High Speed Oscillator (700 kHz max) No Stability Compensation Required Lossless Short Circuit Protection 2.0% Precision Reference Programmable Soft-Start Wide Ambient Temperature Range: Industrial Grade: -40C to 85C Commercial Grade: 0C to 70C Pb-Free Packages are Available
51033 A L Y W x G
MARKING DIAGRAM
8 51033 ALYWx G 1
= = = = = =
Device Code Assembly Location Wafer Lot Year Work Week Continuation of Device Code x = Y or G = Pb-Free Package
PIN CONNECTIONS
1
VGATE PGND COSC GND
VC CS VCC VFB
ORDERING INFORMATION
See detailed ordering and shipping information in the package dimensions section on page 9 of this data sheet.
(c) Semiconductor Components Industries, LLC, 2005
1
October, 2005 - Rev. 10
Publication Order Number: CS51033/D
CS51033
3.3VIN CIN 100 mF RC 10 W
D4 1N5818 D2 1N4148 D3 1N4148
C1 0.1 mF VC V GATE
RG 10 W IRF7404
U1 CS51033
VCC
VFB
0.1 mF
4.7 mH 1.5VOUT @ 3.0 Amp 100
COSC
C2 1.0 mF
C3 100 mF
COSC 150 pF
GND PGND CS
0.1 mF
CS
0.1 mF
D1
C0 100 mF
C4 0.1 mF
100 mF
1N5821 GND RA 1.5 k Note: Capacitors C2, C3, and C4, are low ESR tantalum caps used for noise reduction. RB 300 GND
Figure 1. Typical Application Diagram
MAXIMUM RATINGS
Rating Power Supply Voltage, VCC Driver Supply Voltage, VC Driver Output Voltage, VGATE COSC, CS, VFB (Logic Pins) Peak Output Current Steady State Output Current Operating Junction Temperature, TJ Storage Temperature Range, TS ESD (Human Body Model) Package Thermal Resistance, Lead Temperature Soldering: Junction-to-Case, RqJC Junction-to-Ambient, RqJA Reflow (SMD styles only) (Note 1) Value 5.0 20 20 5.0 1.0 200 150 -65 to 150 2.0 45 165 230 peak Unit V V V V A mA C C kV C/W C/W C
Maximum ratings are those values beyond which device damage can occur. Maximum ratings applied to the device are individual stress limit values (not normal operating conditions) and are not valid simultaneously. If these limits are exceeded, device functional operation is not implied, damage may occur and reliability may be affected. 1. 60 sec. max above 183C.
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CS51033
ELECTRICAL CHARACTERISTICS (Specifications apply for 3.135 VCC 3.465, 3.0 V VC 16 V;
Industrial Grade: -40C < TA < 85C; -40C < TJ < 125C: Commercial Grade: 0C < TA < 70C; 0C < TJ < 125C, unless otherwise specified.) Characteristic Oscillator Frequency Charge Current Discharge Current Maximum Duty Cycle Short Circuit Timer Charge Current Fast Discharge Current Slow Discharge Current Start Fault Inhibit Time Valid Fault Time GATE Inhibit Time Duty Cycle CS Comparator Fault Enable CS Voltage Max CS Voltage Fault Detect Voltage Fault Inhibit Voltage Hold Off Release Voltage Regulator Threshold Voltage Clamp VFB Comparators Regulator Threshold Voltage Fault Threshold Voltage Threshold Line Regulation Input Bias Current Voltage Tracking Input Hysteresis Voltage Power Stage GATE DC Low Saturation Voltage GATE DC High Saturation Voltage Rise Time Fall Time Current Drain ICC IC 3.135 V < VCC < 3.465 V, Gate switching 3.0 V < VC < 16 V, Gate non-switching - - 3.5 2.7 6.0 4.0 mA mA VC = 10 V; VFB = 1.2 V VCOSC = 1.0 V; 200 mA Sink VCOSC = 2.7 V; 200 mA Source; VC = VGATE CGATE = 1.0 nF; 1.5 V < VGATE < 9.0 V CGATE = 1.0 nF; 9.0 V > VGATE > 1.5 V - - - - 1.2 1.5 25 25 1.5 2.1 60 60 V V ns ns VFB = 1.5 V VCS when GATE goes high Minimum VCS VFB = 0 V VCS = 1.5 V VCOSC = VCS = 2.0 V TJ = 25C (Note 2) TJ = -40 to 125C TJ = 25C (Note 2) TJ = -40 to 125C 3.135 V VCC 3.465 VFB = 0 V (Regulator Threshold - Fault Threshold Voltage) - 1.225 1.210 1.12 1.10 - - 70 - 1.250 1.250 1.15 1.15 6.0 1.0 100 4.0 1.275 1.290 1.17 1.19 15 4.0 120 20 V V V V mV mA mV mV VFB = 1.0 V - - - - - 0.4 0.725 2.5 2.6 2.4 1.5 0.7 0.866 - - - - 1.0 1.035 V V V V V V 2.6 V > VCS > 2.4 V 2.4 V > VCS > 1.5 V - VFB = 1.2 V COSC = 470 pF 1.4 V < VCOSC < 2.0 V 2.7 V > VCOSC > 2.0 V 1 - (tOFF/tON) VFB = 1.0 V; CS = 0.1 mF; VCOSC = 2.0 V 1.0 V < VCS < 2.0 V 2.55 V > VCS > 2.4 V 2.4 V > VCS > 1.5 V - 175 40 4.0 0.70 0.2 9.0 2.5 264 66 6.0 0.85 0.3 15 3.1 325 80 10 1.40 0.45 23 4.6 mA mA mA ms ms ms % 160 - - 80.0 200 110 660 83.3 240 - - - kHz mA mA % Test Conditions Min Typ Max Unit
2. Guaranteed by design, not 100% tested in production.
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CS51033
PACKAGE PIN DESCRIPTION
Pin Number 1 2 3 4 5 6 7 8 Pin Symbol VGATE PGND COSC GND VFB VCC CS VC Function Driver pin to gate of external P-Ch FET. Output power stage ground connection. Oscillator frequency programming capacitor. Logic ground. Feedback voltage input. Logic supply voltage. Soft-Start and fault timing capacitor. Driver supply voltage.
VCC RG IC COSC 7IC Oscillator + Comparator A1 - VGATE Flip-Flop G1 R F2 G2 2.5 V S Q A6 + - VFB Comparator 1.25 V - + - + - + Q
VC
VGATE
PGND VFB
1.5 V
0.7 V - + CS Charge Sense Comparator A4 - + - + 2.3 V GND
VCC VCC
Fault Comp
Hold Off Comp
1.15 V - +
G4 G3 IT CS CS Comparator + A2 - - + - + IT 5 G5 2.5 V - A3 + Slow Discharge Comparator
R F1 S
Q
IT 55
Q
1.5 V
Slow Discharge Flip-Flop
2.4 V
Figure 2. Block Diagram
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+ - - + - +
CS51033
CIRCUIT DESCRIPTION THEORY OF OPERATION
Control Scheme
The CS51033 monitors the output voltage to determine when to turn on the P-Ch FET. If VFB falls below the internal reference voltage of 1.25 V during the oscillator's charge cycle, the P-Ch FET is turned on and remains on for the duration of the charge time. The P-Ch FET gets turned off and remains off during the oscillator's discharge cycle time with the maximum duty cycle to 80%. It requires 7.0 mV typical, and 20 mV maximum ripple on the VFB pin to operate. This method of control does not require any loop stability compensation.
Startup
control loop and the output voltage to slowly increase. Once the CS pin charges above the Holdoff Comparator trip point of 0.7 V, the low feedback to the VFB Comparator sets the GATE flip-flop during COSC's charge cycle. Once the GATE flip-flop is set, VGATE goes low and turns on the P-Ch FET. When VCS exceeds 2.4 V, the CS charge sense comparator (A4) sets the VFB comparator reference to 1.25 V completing the startup cycle.
Lossless Short Circuit Protection
The CS51033 has an externally programmable Soft-Start feature that allows the output voltage to come up slowly, preventing voltage overshoot on the output. At startup, the voltage on all pins is zero. As VCC rises, the VC voltage along with the internal resistor RG keeps the P-Ch FET off. As VCC and VC continue to rise, the oscillator capacitor (COSC ) and the Soft-Start/Fault Timing capacitor (CS) charges via internal current sources. COSC gets charged by the current source IC and CS gets charged by the IT source combination described by:
ICS + IT * IT I )T 55 5
The internal Holdoff Comparator ensures that the external P-Ch FET is off until VCS > 0.7 V, preventing the GATE flip-flop (F2) from being set. This allows the oscillator to reach its operating frequency before enabling the drive output. Soft-Start is obtained by clamping the VFB comparator's (A6) reference input to approximately 1/2 of the voltage at the CS pin during startup, permitting the
2.6 V VCS 2.4 V S1 1.5 V 0V TSTART START NORMAL OPERATION S2 S1
The CS51033 has "lossless" short circuit protection since there is no current sense resistor required. When the voltage at the CS pin (the fault timing capacitor voltage ) reaches 2.5 V, the fault timing circuitry is enabled. During normal operation the CS voltage is 2.6 V. During a short circuit or a transient condition, the output voltage moves lower and the voltage at VFB drops. If VFB drops below 1.15 V, the output of the fault comparator goes high and the CS51033 goes into a fast discharge mode. The fault timing capacitor, CS, discharges to 2.4 V. If the VFB voltage is still below 1.15 V when the CS pin reaches 2.4 V, a valid fault condition has been detected. The slow discharge comparator output goes high and enables gate G5 which sets the slow discharge flip-flop. The VGATE flip-flop resets and the output switch is turned off. The fault timing capacitor is slowly discharged to 1.5 V. The CS51033 then enters a normal startup routine. If the fault is still present when the fault timing capacitor voltage reaches 2.5 V, the fast and slow discharge cycles repeat as shown in Figure 3. If the VFB voltage is above 1.15 V when CS reaches 2.4 V a fault condition is not detected, normal operation resumes and CS charges back to 2.6 V. This reduces the chance of erroneously detecting a load transient as a fault condition.
S2 S3 S3 S1
S2 S3 S3
2.5 V
0V td1 tFAULT tRESTART FAULT td2 tFAULT
VGATE 1.25 V 1.15 V VFB
Figure 3. Voltage on Start Capacitor (VGS), the Gate (VGATE), and in the Feedback Loop (VFB), During Startup, Normal and Fault Conditions http://onsemi.com
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CS51033
Buck Regulator Operation
A block diagram of a typical buck regulator is shown in Figure 4. If we assume that the output transistor is initially off, and the system is in discontinuous operation, the inductor current IL is zero and the output voltage is at its nominal value. The current drawn by the load is supplied by the output capacitor CO. When the voltage across CO drops below the threshold established by the feedback resistors R1
and R2 and the reference voltage VREF, the power transistor Q1 switches on and current flows through the inductor to the output. The inductor current rises at a rate determined by (VIN - VOUT)/Load. The duty cycle (or "on" time) for the CS51033 is limited to 80%. If output voltage remains higher than nominal during the entire COSC change time, the Q1 does not turn on, skipping the pulse.
VIN CIN
Q1
L
R1 D1 R2 Control CO RLOAD
Feedback
Figure 4. Buck Regulator Block Diagram
Charge Pump Circuit
(Refer to the CS51033 Application Diagram on page 2). An external charge pump circuit is necessary when the VC input voltage is below 5.0 V to ensure that there is suffifient gate drive voltage for the external FET. When VIN is applied, capacitors C1 and C2 will be charged to a diodes drop below VIN via diodes D2 and D4, respectively. When the P-Ch
FET turns on, it's drain voltage will be approximately equal to VIN. Since the voltage across C1 can not change instantaneously, D2 is reverse biased and the anode voltage rises to approximately 2.0 x 3.3 V - VD2. C1 transfers some of its stored charge C2 via D3. After several cycles there is sufficient gate drive voltage.
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CS51033
APPLICATIONS INFORMATION DESIGNING A POWER SUPPLY WITH THE CS51033
Specifications
* * * * *
VIN = 3.3 V 10% (i.e. 3.63 V max., 2.97 V min.) VOUT = 1.5 V 2.0% IOUT = 0.3 A to 3.0 A Output ripple voltage < 33 mV. FSW = 200 kHz
and the regulator will remain in a continuous conduction mode for lower values of load current. A smaller inductor will result in larger ripple current. The core must not saturate with the maximum expected current, here given by:
I ) DI IMAX + OUT + 3.0 A ) 0.6 A 2.0 + 3.3 A 2.0 4) Output Capacitor
1) Duty Cycle Estimates
Since the maximum duty cycle D, of the CS51033 is limited to 80% min., it is best to estimate the duty cycle for the various input conditions to see that the design will work over the complete operating range. The duty cycle for a buck regulator operating in a continuous conduction mode is given by:
D+ VOUT ) VD VIN * VSAT
The output capacitor limits the output ripple voltage. The CS51033 needs a maximum of 15 mV of output ripple for the feedback comparator to change state. If we assume that all the inductor ripple current flows through the output capacitor and that it is an ideal capacitor (i.e. zero ESR), the minimum capacitance needed to limit the output ripple to 50 mV peak-to-peak is given by:
CO + + 8.0 8.0 DI FSW (200 DV 0.6 A 103 Hz) (33 10*3 V) ^ 11.4 mF
where: VSAT = RDS(ON) x IOUT Max. In this case we can assume that VD = 0.6 V and VSAT = 0.6 V so the equation reduces to:
V D + OUT VIN
The minimum ESR needed to limit the output voltage ripple to 50 mV peak-to-peak is:
*3 ESR + DV + 50 10 + 55 mW DI 0.6 A
From this, the maximum duty cycle DMAX is 53%, this occurs when VIN is at it's minimum while the minimum duty cycle DMIN is 0.35%.
2) Switching Frequency and On and Off Time Calculations
FSW = 200 kHz. The switching frequency is determined by COSC, whose value is determined by:
COSC + FSW 1* 95
FSW 3 106
*
30 103 FSW
2
^ 470 pF
The output capacitor should be chosen so that its ESR is at least half of the calculated value and the capacitance is at least ten times the calculated value. It is often advisable to use several capacitors in parallel to reduce ESR. Low impedance aluminum electrolytic, tantalum or organic semiconductor capacitors are a good choice for an output capacitor. Low impedance aluminum are the cheapest but are not available in surface mount at present. Solid tantalum chip capacitors are available from a number of suppliers and offer the best choice for surface mount applications. The capacitor working voltage should be greater than the output voltage in all cases.
5) VFB Divider VOUT + 1.25 V R1 ) R2 + 1.25 V R1 ) 1.0 R2 R2
T + 1.0 + 5.0 ms FSW TON(MAX) + 5.0 ms TON(MIN) + 5.0 ms 0.53 + 2.65 ms 0.35 + 1.75 ms
TOFF(MAX) + 5.0 ms * 0.7 ms + 4.3 ms 3) Inductor Selection
Pick the inductor value to maintain continuous mode operation down to 0.3 Amps. The ripple current DI = 2 x IOUT(MIN) = 2 x 0.3 A = 0.6 A.
LMIN + VOUT ) VD DI TOFF(MAX) 2.1 V 4.3 ms + ^ 15 mH 0.6 A
The input bias current to the comparator is 4.0 mA. The resistor divider current should be considerably higher than this to ensure that there is sufficient bias current. If we choose the divider current to be at least 250 times the bias current this gives a divider current of 1.0 mA and simplifies the calculations.
1.5 V + R1 ) R2 + 1.5 kW 1.0 mA
Let R2 = 1.0 k Rearranging the divider equation gives:
R1 + R2 VOUT * 1.0 + 1.0 kW 1.5 V + 200 W 1.25 1.25
The CS51033 will operate with almost any value of inductor. With larger inductors the ripple current is reduced
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CS51033
6) Divider Bypass Capacitor CRR
Since the feedback resistors divide the output voltage by a factor of 4.0, i.e. 5.0 V/1.25 V= 4.0, it follows that the output ripple is also divided by four. This would require that the output ripple be at least 60 mV (4.0 x 15 mV) to trip the feedback comparator. We use a capacitor CRR to act as an AC short so that the output ripple is not attenuated by the divider network. The ripple voltage frequency is equal to the switching frequency so we choose CRR so that:
XC + 1.0 2pfC
The fast discharge time occurs when a fault is first detected. The CS capacitor is discharged from 2.5 V to 2.4 V.
TFASTDISCHARGE + CS (2.5 V * 2.4 V) IFASTDISCHARGE
where IFASTDISCHARGE is 66 mA typical.
TFASTDISCHARGE + CS 1515
The recharge time is the time for CS to charge from 1.5 V to 2.5 V.
TCHARGE + CS (2.5 V * 1.5 V) ICHARGE 3787 105)
is negligible at the switching frequency. In this case FSW is 200 kHz if we allow XC = 3.0 W then:
C + 1.0 ^ 0.265 mF 2pf3 7) Soft-Start and Fault Timing Capacitor CS
where ICHARGE is 264 mA typical.
TCHARGE + CS TFAULT + CS
The fault time out time is given by:
(3787 ) 1515 ) 1.5 (1.55 105) 105 + 0.0155
CS performs several important functions. First it provides a dead time for load transients so that the IC does not enter a fault mode every time the load changes abruptly. Secondly it disables the fault circuitry during startup, it also provides Soft-Start by clamping the reference voltage during startup to rise slowly and finally it controls the hiccup short circuit protection circuitry. This function reduces the P-Ch FET's duty cycle to 2.0% of the CS period. The most important consideration in calculating CS is that it's voltage does not reach 2.5 V (the voltage at which the fault detect circuitry is enabled) before VFB reaches 1.15 V otherwise the power supply will never start. If the VFB pin reaches 1.15 V, the fault timing comparator will discharge CS and the supply will not start. For the VFB voltage to reach 1.15 V the output voltage must be at least 4 x 1.15 = 4.6 V. If we choose an arbitrary startup time of 200 ms, we calculate the value of CS from:
T + CS 2.5 V ICHARGE CS(MIN) + 200 ms 264 mA + 0.02 mF 2.5 V
TFAULT + CS
For this circuit
TFAULT + 0.1 10*6 1.55
A larger value of CS will increase the fault time out time but will also increase the Soft-Start time.
8) Input Capacitor
The input capacitor reduces the peak currents drawn from the input supply and reduces the noise and ripple voltage on the VCC and VC pins. This capacitor must also ensure that the VCC remains above the UVLO voltage in the event of an output short circuit. CIN should be a low ESR capacitor of at least 100 mF. A ceramic surface mount capacitor should also be connected between VCC and ground to prevent spikes.
9) MOSFET Selection
Use 0.1 mF. The fault time out time is the sum of the slow discharge time the fast discharge time and the recharge time and is obviously dominated by the slow discharge time. The first parameter is the slow discharge time, it is the time for the CS capacitor to discharge from 2.4 V to 1.5 V and is given by:
TSLOWDISCHARGE + CS (2.4 V * 1.5 V) IDISCHARGE
The CS51033 drives a P-Channel MOSFET. The VGATE pin swings from GND to VC. The type of P-Ch FET used depends on the operating conditions but for input voltages below 7.0 V a logic level FET should be used. Choose a P-Ch FET with a continuous drain current (ID) rating greater than the maximum output current. RDS(ON) should be less than
RDS t+ I 0.6 V 167 mW OUT(MAX)
The Gate-to-Source voltage VGS and the Drain-to-Source Breakdown Voltage should be chosen based on the input supply voltage. The power dissipation due to the conduction losses is given by:
PD + IOUT2 RDS(ON) D
where IDISCHARGE is 6.0 mA typical.
TSLOWDISCHARGE + CS 1.5 V 105
The power dissipation due to the switching losses is given by:
PD + 0.5 VIN IOUT (TRr ) TF) FSW
where TR = Rise Time and TF = Fall Time.
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CS51033
10) Diode Selection
The flyback or catch diode should be a Schottky diode because of it's fast switching ability and low forward voltage drop. The current rating must be at least equal to the
maximum output current. The breakdown voltage should be at least 20 V for this 12 V application. The diode power dissipation is given by:
PD + IOUT VD (1.0 * DMIN)
ORDERING INFORMATION
Device CS51033YD8 CS51033YD8G CS51033YDR8 CS51033YDR8G CS51033GD8 CS51033GD8G CS51033GDR8 CS51033GDR8G 0C < TA < 70C -40C < TA < 85C Operating Temperature Range Package SOIC-8 SOIC-8 (Pb-Free) SOIC-8 SOIC-8 (Pb-Free) SOIC-8 SOIC-8 (Pb-Free) SOIC-8 SOIC-8 (Pb-Free) Shipping 98 Units / Rail 98 Units / Rail 2500 Tape & Reel 2500 Tape & Reel 98 Units / Rail 98 Units / Rail 2500 Tape & Reel 2500 Tape & Reel
For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging Specifications Brochure, BRD8011/D.
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CS51033
PACKAGE DIMENSIONS
SOIC-8 NB CASE 751-07 ISSUE AG
-X- A
8 5
B
1 4
S
0.25 (0.010)
M
Y
M
-Y- G C -Z- H D 0.25 (0.010)
M SEATING PLANE
K
NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSION A AND B DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE. 5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.127 (0.005) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION. 6. 751-01 THRU 751-06 ARE OBSOLETE. NEW STANDARD IS 751-07. MILLIMETERS MIN MAX 4.80 5.00 3.80 4.00 1.35 1.75 0.33 0.51 1.27 BSC 0.10 0.25 0.19 0.25 0.40 1.27 0_ 8_ 0.25 0.50 5.80 6.20 INCHES MIN MAX 0.189 0.197 0.150 0.157 0.053 0.069 0.013 0.020 0.050 BSC 0.004 0.010 0.007 0.010 0.016 0.050 0_ 8_ 0.010 0.020 0.228 0.244
N
X 45 _
0.10 (0.004)
M
J
ZY
S
X
S
DIM A B C D G H J K M N S
SOLDERING FOOTPRINT*
1.52 0.060
7.0 0.275
4.0 0.155
0.6 0.024
1.270 0.050
SCALE 6:1
mm inches
*For additional information on our Pb-Free strategy and soldering details, please download the ON Semiconductor Soldering and Mounting Techniques Reference Manual, SOLDERRM/D.
ON Semiconductor and are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. "Typical" parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including "Typicals" must be validated for each customer application by customer's technical experts. SCILLC does not convey any license under its patent rights nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.
PUBLICATION ORDERING INFORMATION
LITERATURE FULFILLMENT: N. American Technical Support: 800-282-9855 Toll Free Literature Distribution Center for ON Semiconductor USA/Canada P.O. Box 61312, Phoenix, Arizona 85082-1312 USA Phone: 480-829-7710 or 800-344-3860 Toll Free USA/Canada Japan: ON Semiconductor, Japan Customer Focus Center 2-9-1 Kamimeguro, Meguro-ku, Tokyo, Japan 153-0051 Fax: 480-829-7709 or 800-344-3867 Toll Free USA/Canada Phone: 81-3-5773-3850 Email: orderlit@onsemi.com ON Semiconductor Website: http://onsemi.com Order Literature: http://www.onsemi.com/litorder For additional information, please contact your local Sales Representative.
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CS51033/D

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